Phase detection in a sync pulse generator

ABSTRACT

A phase detector and phase detection method for a sync pulse generator operable in a clock synchronizer that effectuates data transfer between first circuitry disposed in a first clock domain and second circuitry disposed in a second clock domain. The first clock domain is operable with a first clock signal and the second clock domain is operable with a second clock signal. At least one first flip flop is operable to sample the first clock signal with a rising edge of the second clock signal and at least one second flip flop is operable to sample the first clock signal with a falling edge of the second clock signal. The sampling produces transitions indicative of the coincident rising edges between the first and second signals.

CROSS-REFERENCE TO RELATED APPLICATION(S)

This application discloses subject matter related to the subject matterdisclosed in the following commonly owned co-pending patentapplications: (i) “PROGRAMMABLE SYNC PULSE GENERATOR,” filed ______;application Ser. No. ______ (Docket No. 200315339-1), in the name(s) of:Richard W. Adkisson and Ryan L. Akkerman; (ii) “DRIFT-TOLERANT SYNCGENERATION CIRCUIT FOR A SYNC PULSE GENERATOR,” filed ______;application Ser. No. ______(Docket No. 200315340-1), in the name(s) of:Richard W. Adkisson; (iii) “PROGRAMMABLE CLOCK SYNCHRONIZER,” filed Jul.30, 2003; application Ser. No. 10/630,159 (Docket No. 200207722-2), inthe name(s) of: Richard W. Adkisson; and (iv) “PHASE DETECTOR FOR APROGRAMMABLE CLOCK SYNCHRONIZER,” filed Jul. 30, 2003; application Ser.No. 10/630,298 (Docket No. 200208010-1), in the name(s) of: Richard W.Adkisson, all of which are hereby incorporated by reference for allpurposes.

BACKGROUND

Digital electronic systems, e.g., computer systems, often need tocommunicate using different interfaces, each running at an optimizedspeed for increased performance. Typically, multiple clock signalshaving different frequencies are utilized for providing appropriatetiming to the interfaces. Further, the frequencies of such clock signalsare generally related to one another in a predetermined manner. Forexample, a link or system clock running at a particular frequency (F₁)may be utilized as a master clock in a typical computer system forproviding a time base with respect to a specific portion of its digitalcircuitry. Other portions of the computer system's digital circuitry(such as a core segment and the logic circuitry disposed thereon) may beclocked using timing signals derived from the master clock wherein thederived frequencies (F_(d)) follow the relationship: F₁/F_(d)≧1.

Because of the asynchronous—although related—nature of the constituentdigital circuit portions, synchronizer circuitry is often used incomputer systems to synchronize data transfer operations across a clockdomain boundary so as to avoid timing-related data errors. Suchsynchronizer circuitry is typically required to possess low latency(which necessitates precise control of the asynchronous clocks thatrespectively clock the circuit portions in two different clock domains).Typically, phase-locked loops (PLLs) are utilized in conventionalsynchronizer circuitry arrangements to produce clocks of different yetrelated frequencies. Synchronization pulse generation having phasedetection capability and drift tolerance would be beneficial inapplications where PLLs are deficient.

SUMMARY

A phase detector and phase detection method are disclosed for a syncpulse generator operable in a clock synchronizer that effectuates datatransfer between first circuitry disposed in a first clock domain andsecond circuitry disposed in a second clock domain. The first clockdomain is operable with a first clock signal and the second clock domainis operable with a second clock signal. At least one first flip flop isoperable to sample the first clock signal with a rising edge of thesecond clock signal and at least one second flip flop is operable tosample the first clock signal with a falling edge of the second clocksignal. The sampling produces transitions indicative of the coincidentrising edges between the first and second signals.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 depicts a block diagram of an embodiment of a synchronizer systemfor effectuating data transfer across a clock boundary;

FIG. 2 depicts a functional block diagram of one embodiment of a syncpulse generator operable with the synchronizer system shown in FIG. 1;

FIG. 3 depicts a schematic diagram of one embodiment of phase detectioncircuitry of the sync pulse generator shown in FIG. 2;

FIG. 4 depicts a timing diagram associated with the phase detectioncircuitry of FIG. 3;

FIG. 5A depicts a schematic diagram of a portion of one embodiment ofvalidation circuitry of the sync pulse generator shown in FIG. 3;

FIG. 5B depicts a schematic diagram of another portion of the validationcircuitry illustrated in FIG. 5A;

FIG. 5C depicts a schematic diagram of another portion of the validationcircuitry illustrated in FIG. 5A;

FIG. 6 depicts a timing diagram illustrating different skews that mayassociated with clock signals;

FIG. 7A depicts a table further illustrating the different skewsassociated with rising clock edges of the clock signals;

FIG. 7B depicts a table further illustrating the different skewsassociated with falling clock edges of the clock signals;

FIG. 8 depicts a table illustrating the different skews associated withthe rising and falling clock edges relative to operational modes of thevalidation circuitry;

FIG. 9 depicts a block schematic diagram of one embodiment of syncgeneration circuitry;

FIG. 10 depicts a timing diagram associated with the sync generationcircuitry of FIG. 9;

FIG. 11 depicts a flow chart of one embodiment of a sync pulsegeneration method;

FIG. 12 depicts a flow chart of one embodiment of a phase detectionmethod;

FIG. 13 depicts a flow chart of one embodiment of a sync generationmethod;

FIG. 14A depicts a portion of an additional timing diagram associatedwith one embodiment of the sync pulse generator of FIG. 2; and

FIG. 14B depicts another portion of the timing diagram presented in FIG.14A.

DETAILED DESCRIPTION OF THE DRAWINGS

In the drawings, like or similar elements are designated with identicalreference numerals throughout the several views thereof, and the variouselements depicted are not necessarily drawn to scale. Referring now toFIG. 1, therein is depicted an embodiment of a synchronizer system 100for effectuating data transfer across a clock boundary between a firstclock domain (i.e., “fast clock domain”) having N clock cycles and asecond clock domain (e.g., “slow clock domain”) having M clock cyclessuch that N/M>1. Typically, M=(N−1), and by way of exemplaryimplementation, the synchronizer system 100 may be provided as part of acomputer system for transferring data between a faster clock domain(e.g., operating with a link clock signal of 333 MHz) and a slower clockdomain (e.g., operating with a core clock signal of 267 MHz), with a 5:4frequency ratio. Accordingly, for purposes of this present patentapplication, the terms “first clock” and “link clock” will be usedsynonymously with respect to a fast clock domain; likewise, the terms“second clock” and “core clock” will be used with respect to a slowclock domain. It should be appreciated, however, that the synchronizerpulse generator (or, sync pulse generator) described herein may haveapplications with respect to other clock domains, such as a coreclock/bus clock domain interface, for example.

A phase-locked loop (PLL) circuit 104 is operable to generate a linkclock (i.e., first clock) signal 108 (designated as link_clock) based ona system clock 109 (designated as sys_clk) provided thereto. The PLLcircuit 104 is also operable to generate a core clock (i.e., secondclock) signal 106 (designated as core_clock) based on the system clocksignal. Each of the core_clock 106 and link_clock signals 108 is firstprovided to a respective clock distribution tree block for generating adistributed clock signal that is provided to various parts of asynchronizer/controller block 102 provided for the synchronizer system100. Reference numeral 112 refers to the clock distribution treeoperable with the core_clock signal 106 to generate the distributedcore_clock signal, which is labeled as “c” and shown with referencenumeral 106′ in FIG. 1. Likewise, reference numeral 114 refers to theclock distribution tree 114 operable with the link_clock signal 108 togenerate the distributed link_clock signal, which is labeled as “1” andshown with reference numeral 108′ in FIG. 1. As one skilled in the artshould readily recognize, the distributed clock signals are essentiallythe same as the input clock signals. Accordingly, the system clocksignal 109, core_clock signal 106 and its distributed counterpart c 106′are treated equivalently hereinafter. Also, the link_clock signal 108and its distributed counterpart l 108′ are similarly treated asequivalent.

A synchronization (SYNC) pulse generation circuit 116 is operableresponsive to the clock signals 106, 108, to generate a pair of SYNCpulses that are forwarded to appropriate domains of the synchronizercontroller circuitry. The SYNC pulses, which are designated sync_c 118and sync_l 120, provide a reference point for coordinating data transferoperations and are driven HIGH when the link_clock and core_clocksignals have coincident rising edges. The two clock signals 106, 108 andSYNC pulse signals are provided to the synchronizer/controller block 102that straddles the clock boundary between the first clock domain (i.e.,link clock domain) and the second clock domain (i.e., core clock domain)for effectuating data transfer across the boundary. Reference numerals103A and 103B refer to circuitry disposed in the first and second clockdomains, respectively, e.g., link clock domain logic and core clockdomain logic, that transmit and receive data therebetween as facilitatedvia synchronizers 105A and 105B, which will be described in greaterdetail hereinbelow.

A link clock synchronizer controller 122 is operable responsive to thedistributed link_clock, l 108′, and sync_l pulse 120 to generate aplurality of synchronizer control signals, a portion of which signalsare directed to a first synchronizer circuit means 105A operating tocontrol data transfer from first circuitry 103A (i.e., link clock domainlogic) to second circuitry 103B (i.e., core clock domain logic).Reference numeral 132 refers to the signal path of this portion ofcontrol signals emanating from the link clock synchronizer controller122. Another portion of the synchronizer control signals generated bythe link clock synchronizer controller 122 are directed (via signal path134) to a second synchronizer circuit means 105B operating to controldata transfer from second circuitry 103B to first circuitry 103A.Consistent with the nomenclature used in the present patent application,the first and second synchronizer circuits may also be referred to aslink-to-core synchronizer and core-to-link synchronizer circuits,respectively. In addition, the core clock synchronizer controller 124also generates a set of inter-controller control signals that areprovided to the first synchronizer controller 122 (i.e., link clocksynchronizer controller) such that both controllers can work together.Reference numeral 128 refers to the signal path of the inter-controllercontrol signal(s) provided between the link clock synchronizer 122 andthe core clock synchronizer controller 124.

Similar to the operation of the link clock synchronizer controller 122,the core clock synchronizer controller 124 is operable responsive to thedistributed core_clock, c 106′, inter-controller control signals andsync_c pulse 118 to generate a plurality of synchronizer controlsignals, a portion of which signals are directed to the firstsynchronizer circuit means 105A and another portion of which signals aredirected to the second synchronizer circuit means 105B. Referencenumerals 138 and 140 refer to the respective signal paths relating tothese control signals.

The link clock synchronizer controller 122 is also operable to generatedata transmit/receive control signals that are provided to the linkclock domain logic 103A via signal path 136 in order that the link clockdomain logic 103A knows when it can send data to the core clock domainlogic 103B (i.e., valid TX operations) and when it can receive data fromthe core clock domain logic 103B (i.e., valid RX operations).

Additionally, an optional phase detector 130 detects phase differences(i.e., skew) between the two clock signals by operating responsive tothe sampled link_clock and core_clock signals. This information isprovided to the link clock synchronizer controller 122, which cancompensate for the skew or determine appropriate times to coordinatewith the core clock synchronizer controller 124. Further detailsregarding the various sub-systems described hereinabove may be found inthe following commonly owned co-pending patent application: PROGRAMMABLECLOCK SYNCHRONIZER,” filed Jul. 30, 2003; application Ser. No.10/630,159 (Docket No. 200207722-2), in the name(s) of: Richard W.Adkisson; which is hereby incorporated by reference for all purposes.

As set forth above and in the cross-referenced U.S. patent application,the synchronizer system 100 may be programmed for different skewtolerances and latencies, so that data transfer at high speeds canproceed properly even where there is a high skew or requirement of lowlatency. Further, the synchronizer system 100 can operate with any twoclock domains having a ratio of N first clock cycles to M second clockcycles, where N/M≧1. It should be appreciated that the synchronizersystem 100 is presented by way of example and not by way of limitation.The synchronizer system 100 is one embodiment of a synchronizer systemin which the sync pulse generation circuit 116 may be utilized. In thisgeneral regard, the link clock synchronizer controller 122, core clocksynchronizer controller 124, link domain logic 103A, and firstsynchronizer 105A effectuate first synchronization circuitry whichtransfers data from the link clock domain to the core clock domain.Likewise, link clock synchronizer controller 122, core clocksynchronizer controller 124, core domain logic 103B, and secondsynchronizer 105B effectuate second synchronization circuitry whichtransfers data from the core clock domain to the link clock domain.

FIG. 2 depicts a schematic diagram of one embodiment of the sync pulsegenerator 116 which includes internal phase detection circuitry 200,validation circuitry 202, and a sync generation circuit 204. The phasedetection circuitry 200 includes a phase detector circuit 206 that isoperable to sample the link clock signal with the core clock signal todetermine coincident rising edges of the link and core clock signals. Asillustrated, a cr_edge signal (a first sampled clock signal) and acf_edge signal (a second sampled clock signal) asserted by the phasedetector circuit are indicative of the coincident rising edges.Specifically, the cr_edge signal is generated by sampling the link clocksignal with the rising edge of the core clock signal. In one embodiment,the cr_edge signal having a zero-to-one transition therein is assertedprior to an occurrence of the coincident rising edges between the linkand core clock signals. On the other hand, the cf_edge signal isasserted upon sampling the link clock signal with the falling edge ofthe core clock signal. In one embodiment, similar to the cr_edge signal,the cf_edge signal having a one-to-zero transition therein is assertedprior to an occurrence of the coincident rising edges in the link andcore clock signals.

The phase detection circuitry 200 also includes a staging registerportion 208 which receives the cr_edge and cf_edge signals from thephase detector circuit 206. The staging register portion 208 may includeany number of delay registers which appropriately delay the cr_edge andcf_edge signals before the signals are processed by the validationcircuitry 202. As will be explained in further detail hereinbelow, thenumber of registers employed is related to the ratio of the clock cyclesbetween the link clock domain and the core clock domain. For example, inthe case of a 5:4 ratio between the link clock domain and the core clockdomain, six registers, i.e., registers 0 through 5, may be appropriate.

The validation circuitry 202 includes a valid edge detect circuit 210and a timeout counter 212 having a register 214. The valid edge detectcircuit 210 receives the delayed cr_edge and cf_edge signals as well asa ratio signal indicative of the ratio between the link clock and thecore clock signals. Additionally, a mode signal is driven to the validedge detect circuit to select the appropriate level of skew tolerance.In one embodiment, the mode signal is programmable. As will be furtherexplained, the valid edge detect circuit 210 validates the coincidentedges, e.g., coincident rising edges indicated by the cr_edge andcf_edge signals, based upon skew tolerance between the first and secondclock signals. For example, in one exemplary mode of operation, thevalid edge detect circuit 210 is operable to compensate for a skew ofless than the following:(period of the core clock signal)/2−(period of the link clock signal)/2

In another exemplary mode of operation, the valid edge detect circuit210 and timeout counter 212 are operable to compensate for a skew ofless the following:(period of the core clock signal)−(period of the link clock signal)

Upon validating the coincident rising edges, the valid edge detectcircuit 210 drives a valid edge signal; namely, edge_valid, which isreceived by the sync generation circuit 204 that generatessynchronization pulses in both the link clock domain and core clockdomain. The sync generation circuit 204 utilizes the ratio signal inconjunction with the edge_valid signal and a feedback loop tocontinuously generate the synchronization pulses in both the core andlink clock domains. The synchronization pulses generated in the linkclock domain are indicated as sync_l. Similarly, the synchronizationpulses generated in the core clock domain are indicated as sync_c.

FIG. 3 depicts a block schematic diagram of one embodiment of a circuitportion 300 that includes the phase detection circuitry 200 operable toprovide an indication of the coincident rising edges between the clocksused in the synchronizer system 100. As previously discussed, the phasedetection circuitry 200 comprises phase detector circuit 206 and delayblock 208 including at least one register. In general, the phasedetector circuit 206 employs the rising and falling edges of thenon-distributed core_clock 106 to sample the non-distributed link_clock108. In one implementation, the equivalent distributed clock signals maybe used instead. Accordingly, by way of illustrative implementation, thelink_clock l 108′ is sampled by at least one first flip flop clocked onthe rising edge of the core_clock c 106′. As illustrated, flip flops 302and 304 sample the link_clock l 108′ with the rising edge of thecore_clock c 106′. By employing two flip flops for sampling, the phasedetector circuit 206 is able to decrease metastability. Flip flop 302asserts the sampled link_clock l 108′ signal as a pd_cr1_ff signal whichis sampled via the flip flop 304 and asserted as a pd_cr2_ff signal. Aflip flop 306 maintains timing by staging the pd_cr2_ff signal such thata pd_cr3_ff signal is asserted which is driven to a flip flop 308 and anAND gate 310. The AND gate 310 has a second input, which is inverted,supplied by a pd_cr4_ff signal generated by the flip flop 308. The ANDgate 310 asserts the cr_edge signal when the pd_cr3_ff signal isasserted and the pd_cr4_ff signal is deasserted. Hence the cr_edgesignal is asserted having a zero-to-one transition that is indicative ofcoincident rising edges between the first and second clock signals. Thecr_edge signal is driven to the delay register block 208 which, asillustrated, includes a sequence of flip flops 312-322 each having a tapthat provides an input to the valid edge detector circuit 210.Specifically, the flip flop 312 receives the cr_edge signal and assertsa cr_edge_ff[0] signal which is sent to the flip flop 314 and the validedge detector circuit 210. Similarly, the flip flop 314 asserts acr_edge_ff[l] signal, the flip flop 316 asserts a cr_edge_ff[2] signal,the flip flop 318 asserts a cr_edge_ff[3] signal, the flip flop 320asserts a cr_edge_ff[4] signal, and the flip flop 322 asserts acr_edge_ff[5] signal. In one embodiment, the asserted sampled clocksignal (i.e., cr_edge) may be registered N+1 times, wherein, forexample, N+1 is 6 if 5:4 is the largest ratio detected. Taps areselected off the registers and implemented by the valid edge detectorcircuit 210 using a scheme that will be described in greater detailhereinbelow.

Similarly, the link_clock l 108′ is sampled by at least one second flipflop clocked on the falling edge of the core_clock c 106′. Asillustrated, flip flops 324 and 326 sample the link_clock l 108′ withthe falling edge of the core_clock c 106′. Flip flop 324 asserts thesampled link_clock l 108′ signal as a pd_cf1_ff signal which is sampledand asserted by the flip flop 326 as a pd_cf3_ff signal. A flip flop 328delays the pd_cf3_ff signal to ensure timing and asserts a pd_cf3_ffsignal that is received by a flip flop 330 and an AND gate 332. The ANDgate inverts the pd_cf3_ff input and receives a second input signal fromthe flip flop 330 in the form of a pd_cf4_ff signal. The AND gate 332asserts the cf_edge signal (i.e., the second sampled clock signal)indicative of coincident rising edges upon detecting an asserted logiclow pd_cf3_ff signal and an asserted logic high pd_cf4_ff signal. Hencethe cf_edge signal having a one-to-zero transition is asserted that isindicative of an occurrence of coincident rising edges between the firstand second clock signals. The cf_edge signal is forwarded to the delayregister block 208 which, as illustrated, includes a sequence of flipflops 334-344 each having a tap that provides an input to the valid edgedetector 210 wherein the flip flops 334, 336, 338, 340, 342 and 344assert cf_edge_ff[0], cf_edge_ff[1], cf_edge_ff[2], cf_edge_ff[3],cf_edge_ff[4] and cf_edge_ff[5] signals, respectively. In theillustrated embodiment, the phase detection circuitry 200 uses flipflops; however, it should be appreciated that the phase detectioncircuitry 200 may be realized in a variety of digital logic componentssuch as latches, delay lines, et cetera. Moreover, although the phasedetection circuitry 200 is described in relation to positive logic,negative logic may also be employed to determine the phase difference.It should be further appreciated that although the logic herein isdescribed relative to coincident rising edges, the teachings of thepresent patent application are applicable to coincident falling edges aswell.

FIG. 4 depicts a timing diagram 400 associated with the circuit portion300 of FIG. 3 wherein a clock frequency ratio of 5:4 is exemplifiedbetween the link_clock signal and core_clock signal. A cycle countrefers to the numbering of core_clock cycles in a particular timingsequence. In particular, the timing diagram 400 illustrates the outputof flip flops 324-330, AND gate 332, and flip flops 334 and 336 aspd_cf1_ff, pd_cf3_ff, pd_cf3_ff, pd_cf4_ff, cf_edge, cf_edge_ff[0], andcf_edge_ff[l], respectively. Additionally, the output of valid edgedetector circuit 210 is represented as edge_valid. As illustrated, thesignals include logic data levels comprising 0s or 1s. For purposes ofexplanation, only the timing diagram of the falling edge portion of thephase detection circuitry 200 is exemplified. It should be appreciatedthat the rising edge portion of the phase detection circuitry 200 has asimilar operation (i.e., generation of the cr_edge signal and subsequentdelay registration).

As previously discussed, the flip flop 324 samples the link clock signal108′ with the falling edge of the core clock signal 106′ as indicated byreference numerals 402-410. In the illustrated embodiment, this producesa [1001] sequence of logic levels. Since the flip flop 326 samples thepd_cf1_ff signal also with the falling edge of the core clock signal106′, the levels of the pd_cf3_ff signal are shifted by one cycle. Theflip flop 328 samples the pd_cf3_ff signal and delays the signal by ahalf-cycle, thereby shifting the data of the pd_cf3_ff by one-half of acycle relative to the data of the pd_cf3_ff signal. The flip flop 330samples the pd_cf3_ff and delays the signal by a full cycle. The data ofthe pd_cf4_ff signal of the flip flop 330 is therefore the data of thepd_cf3_ff signal shifted by one full cycle. The AND gate 332 receivesboth the pd_cf3_ff signal and the pd_cf4_ff signal and asserts logiclevel of 1 as the cf_edge signal when a one-to-zero transition isdetected, i.e., when the pd_cf3_ff data is logic low and the pd_cf4_ffis asserted logic high. In the illustrated embodiment, this one-to-zerotransition condition is indicated by reference numerals 412 and 414.

The detected transitions, which are indicative of coincident risingedges, are validated by the valid edge circuit 210 based on the mode ofskew tolerance and the ratio. Continuing with the illustrated example,the cf_edge, cf_edge_ff [0], and cf_edge_ff [1] signals are forwarded tothe valid edge detector circuit 210. No skew is present between thelink_clock signal and the core_clock signal and, as mentioned, the clockratio between the link_clock signal and the core_clock signal is 5:4.Hence, upon detecting a current falling edge condition, which will beexplained in detail hereinbelow, the valid edge detector circuit assertsthe edge_valid signal logic high.

As previously mentioned, the valid edge detector 210 may be set for anyone of four modes of operation. An Assume Start Stable mode provides askew tolerance of less than (core period/2−link period/2) or 1/8 of alink period for the 5:4 ratio. In this mode of operation, the coincidentrising edges are validated upon a current falling edge condition asindicated by reference numeral 416 with which the following logic isassociated:˜cf_edge & cf_edge_ff[0] & ˜cf_edge_ff[1]

A second Assume Start Stable mode, i.e., an Assume Start Stable 2 mode,also provides a skew tolerance of less than (core period/2−linkperiod/2) or 1/8 of a link period for the 5:4 ratio. In this mode ofoperation, the coincident rising edges are validated upon theaforementioned current falling edge combination being detected twicesequentially. For example, the current falling edge condition isdetected in two sequential cycles, thereby minimizing the risk ofdetecting coincident edges caused by aliasing. A Wait-for-Zero modeprovides a skew tolerance of less than (core period−link period) or 2/8of a link period at the 5:4 ratio. In this mode of operation, the validedge signal (edge_valid) is asserted upon detecting a zero crossingcondition in the sampled cr_edge clock signal and a constant fallingedge condition in the sampled cf_edge clock signal. A secondWait-for-Zero mode, i.e., a Wait-for-Zero 2 mode, also provides a skewtolerance of less than (core period−link period) or 2/8 of a link periodat the 5:4 ratio. In the second Wait-for-Zero mode, the valid edgedetector circuit asserts the edge_valid signal after detecting a zerocrossing condition in the sampled cr_edge clock signal and a constantfalling edge condition in the sampled cf_edge clock signal.Alternatively, the edge_valid signal may be generated in this mode aftera timeout when no zero crossing is detected after a specified period oftime. Specifically, timeout counter 212 (shown in FIG. 2), whichutilizes a feedback loop that in one embodiment includes atimeout_count_ff[11:0] signal, asserts the timeout signal after thespecified period of time lapses. Once the timeout period occurs, thevalid edge detector shifts to the Assume Start Stable 2 mode.

FIG. 5A depicts a schematic diagram of a circuit block 500A which formsa part of the synchronization pulse generation circuit 116. Aspreviously discussed, the cf_edge signal is driven from phase detectorcircuit 206 to at least one delay register 208 which in one embodimentincludes a plurality of flip flops 334-344. The valid edge detectcircuit 210 includes AND gates 502-506 which receive taps from the flipflops 334-344. The AND gate 502 asserts a curr_cf_edge signal upondetecting a current falling edge condition. The first input of the ANDgate 502 is the inverted cf_edge_ff[1] signal provided by the flip flop336. The second input is the cf_edge_ff[0] signal provided by the flipflop 334 and the third input is the inverted cf_edge signal. Hence, thelogic for detecting the current falling edge condition is as follows:˜cf_edge_ff[1] & cf_edge_ff[0] & ˜cf_edge

The AND gate 504 asserts a prev_cf_edge_(—)54 signal upon detecting aprevious falling edge condition for a clock ratio of 5:4. The firstinput provided to the AND gate 504 is the inverted cf_edge_ff[5] signalfrom the flip flop 344. The second input is the cf_edge_ff[4] signalfrom the flip flop 342 and the third input is the inverted cf_edge_ff[3]signal from the flip flop 340. Therefore, the logic for detecting theprevious falling edge condition for a clock ratio of 5:4 is as follows:˜cf_edge_ff[5] & cf_edge_ff[4] & ˜cf_edge_ff[3]

The AND gate 506 asserts a prev_cf_edge_(—)43 signal upon detecting aprevious falling edge condition for a clock ratio of 4:3. The firstinput provided to the AND gate 506 is the inverted cf_edge_ff[4] signalfrom the flip flop 342. The second input is the cf_edge_ff [3] signalfrom the flip flop 340 and the third input is the inverted cf_edge_ff[2]signal from the flip flop 338. Therefore, the logic for detecting theprevious falling edge condition for a clock ratio of 4:3 is as follows:˜cf_edge_ff[4] & cf_edge_ff[3] & ˜cf_edge_ff[2]

A multiplexer (MUX) circuit 508, which is under the control of the ratiosignal, receives the prev_cf_edge_(—)54 signal and theprev_cf_edge_(—)43 signal. When the clock ratio between the link clockdomain and the core clock domain is 5:4, the ratio signal is set to[10]. On the other hand, when the clock ratio is 4:3, the ratio signalis set to [01]. Under the control of the ratio signal, the MUX circuit508 appropriately selects the prev_cf_edge_(—)54 signal or theprev_cf_edge_(—)43 signal for assertion as a prev_cf_edge signal that isindicative of the previous falling edge condition discussed hereinabove.It should be appreciated that ratios other than 5:4 and 4:3 may beaccommodated by increasing the number of AND gates and MUX circuits aswell as increasing the width of the ratio signal.

FIG. 5B depicts a schematic diagram of a circuit block 500B which formsanother part of the synchronization pulse generation circuit 116.Whereas FIG. 5A described above illustrated the processing of thecf_edge signal relative to falling edge conditions, FIG. 5B illustratesthe processing of the cr_edge signal relative to rising edge conditions.The circuit block 500B includes a portion of the delay register 208including flip flops 312-320. Additionally, a portion of the valid edgedetect circuit 210 having a plurality of AND gates is included in thecircuit block 500B. Specifically, AND gates 510-520 process the signalsprovided by the taps from the delay register 208. Further, MUX circuits522-524 process the signals generated by corresponding segments of theAND gates 510-520.

The AND gate 510 generates a curr_cr_plus signal indicative of a currentrising edge plus condition. The cr_edge_ff[0] signal provides a firstinput to the AND gate 510 that is inverted. The cr_edge signal providesa second input to the AND gate 510. Hence, the logic for detecting thecurrent rising edge plus condition is as follows:˜cr_edge_ff[0] & cr_edge

The AND gate 512 asserts a prev_cr_plus_(—)54 signal indicative of aprevious rising edge plus condition for a 5:4 clock ratio by ANDing theinverted cr_edge_ff[4] signal with the cr_edge_ff[3] signal. Similarly,the AND gate 514 asserts a prev_cr_plus_(—)43 signal indicative of aprevious rising edge plus condition for 4:3 clock ratio by ANDing theinverted cr_edge_ff[3] signal with the cr_edge_ff[2] signal. The MUXcircuit 522 under the control of the ratio signal appropriately selectsthe prev_cr_plus_(—)54 signal or the prev_cr_plus_(—)43 signal dependingon the clock ratio.

The AND gate 516 asserts a curr_cr_minus signal indicative of a currentrising edge minus condition by ANDing the cr_edge_ff[0] signal andinverted cr_edge signal. The AND gate 518 asserts a prev_cr_minus 54signal indicative of a previous rising edge minus condition for a 5:4ratio by ANDing the cr_edge_ff[4] signal and inverted cr_edge_ff[3]signal. The AND gate 520 asserts a prev_cr_minus_(—)43 signal indicativeof a previous rising edge minus condition for a 4:3 ratio by ANDing thecr_edge_ff[3] signal and inverted cr_edge_ff[2] signal. The MUX circuit524 under the control of the ratio signal appropriately selects theprev_cr_mins_(—)54 signal or the prev_cr_minus_(—)43 signal depending onthe clock ratio.

FIG. 5C depicts a circuit block 500C defining a further potion of thevalid edge detect circuit 210. MUX circuit 526, which is under thecontrol of the mode signal, determines the operational mode of the validedge detect circuit 210 as described by the following table: TABLE 1Mode Signal and Operation Mode Mode Signal [1:0] Selected OperationalMode 00 Assume Start Stable 01 Assume Start Stable 2 10 Wait-for-Zero 11Wait-for-Zero 2

With respect to the Assume Start Stable mode, when the mode signal isset to [00], the curr_cf_edge signal is selected and asserted as theedge_valid signal. The logic for the Assume Start Stable mode is asfollows:˜cf_edge_ff[1] & cf_edge_ff[0] & ˜cf_edge

With respect to the Assume Start Stable 2 mode, when the mode signal isset to [01], an AND gate 528 ANDs the curr_cf_edge signal and theprev_cf_edge signal provided by the MUX circuit 508 to assert anassume_start_stable2 signal which, in turn, is asserted as theedge_valid signal by the MUX circuit 526. In the Assume Start Stable 2mode, both the current falling edge condition and previous falling edgecondition must be satisfied before the edge_valid signal is asserted.This ensures that the skew has changed little between the two samplesand thus avoids aliasing. By way of example, the logic for the AssumeStart Stable 2 mode for the 5:4 ratio is as follows:(˜cf_edge_ff[1] & cf_edge_ff[0] & ˜cf_edge) & (˜cf_edge_ff[5] &cf_edge_ff[4] & ˜cf_edge_ff[3])

With respect to the Wait-for-Zero mode, when the asserted mode signal is[10], an AND gate 530 ANDs the curr_cr_plus signal provided by the ANDgate 510 and the prev_cr_minus signal provided by the MUX circuit 524 toassert a currp_prevm signal. An AND gate 532 ANDs the currp_prevm signalwith the assume_start_stable2 signal to assert a wait1 signal which isforwarded to an OR gate 534. The second input of the OR gate 534 isgenerated by AND gates 536 and 538. Specifically, the AND gate 536 ANDsthe curr_cr_minus signal provided by the AND gate 516 with theprev_cr_plus signal provided by the MUX circuit 522 to assert acurrm_prevp signal. The AND gate 538 ANDs the assume_start_stable2signal and the currm_prevp signal in asserting a wait2 signal.

The OR gate 534 ORs the wait1 signal and wait2 signal in asserting await_for_zero signal which, in the Wait-for-Zero mode, is selected bythe MUX circuit 526 for assertion as the edge_valid signal. TheWait-for-Zero mode sets edge_valid upon the detection of a zero crossingcondition which occurs when the rising edge jumps forward or backwardbetween previous and current samples but the falling edge staysconstant. As will be appreciated, the forward and backward jumps of therising edge are detected by the logic associated with AND gates 530 and536. By way of example, the logic for the Wait-for-Zero mode for the 5:4ratio is as follows:{[(˜cr_edge_ff[0] & cr_edge) & (cr_edge_ff[4] &˜cr_edgeff[3])] & assume_start_stable2} OR {[(cr_edge_ff[0] & ˜cr_edge)& (˜cr_edge_ff[4] & cr_edgeff[3])] & assume_start_stable2}

With respect to the Wait-for-Zero 2 mode, when the mode signal isasserted [11], the assume_start_stable2 signal provided by the AND gate528 and the wait_for_zero signal provided by the OR gate 534 providefirst and second inputs to a MUX circuit 540 that operates under thecontrol of the timeout signal. The MUX circuit 540 enables the validedge detector circuit 210 to switch from the Wait-for-Zero mode to theAssume Start Stable 2 mode if no zero crossing is detected after apredetermined timeout period as determined by the timeout counter 212 ofFIG. 3. This mode of operation that includes the zero crossing timeoutcondition is particularly useful when a small offset is present and theskew is small enough that no zero crossing is going to occur. As opposedto waiting indefinitely for the zero crossing, which is not going tooccur, the Wait-for-Zero 2 mode switches to the Assume Start Stable 2mode.

FIG. 6 depicts a timing diagram 600 illustrating different skews betweenthe link and core clock signals for a 5:4 clock ratio. A cycle countrefers to the numbering of core_clock cycles in a particular timingsequence. The coincident rising edges between a core_clock signal 602and a link_clock signal 604 are represented by arrows 606 and 608,respectively, where there is no skew between the core_clock and thelink_clock signals. As previously discussed, the synchronizer pulsegenerator circuit described herein is operable to compensate for variousskews. By way of example, core_clock signals 610-614 represent skews of+1.125 ns, +0.75 ns, and +0.375 ns, respectively, where arrows 616-620represent the rising edges with respect to rising edge 608 of thelink_clock 604. Similarly, core_clock signals 622-626 represent skews of−0.375 ns, −0.75 ns, and −1.125 ns, respectively. For these negativeskews, the corresponding rising edges in the core_clocks are representedby arrows 628-632. It should be appreciated that skews depicted in FIG.6 are exemplary and other skews that may exist between the core_clockand the link_clock are within the teachings of the present patentapplication.

FIG. 7A depicts a table 700 further illustrating the different skewsassociated with rising clock edges of the signals depicted in FIG. 6.Rows 610 r-614 r are tabular representations of the logic levels andskew data associated with core_clock signals 610-614. Similarly, row 602r is a tabular representation of the data associated with core_clocksignal 602 and rows 622 r-624 r are tabular representations of the dataassociated with core_clock signals 622-626. Columns 702-716 correspondto the cycle count and the number of core_clock cycles in a particulartiming sequence. An “r” denotes rising, an “f” denotes falling (see FIG.7B), a “p1” denotes plus one (+1) skew, “p2” denotes plus two (+2) skew,“m1” denotes minus one (−1) skew, and “m2” denotes minus two (−2) skew.Plus skew, or positive skew is defined as the condition where the linkclock's normal coincident rising edge occurs first, followed by thecorresponding rising edge in the core clock signal. Similarly, the minusor negative skew indicates that the core clock is leading the linkclock. For example, the indication 3-rp1 in column 708 indicates thatthe cycle count for column 708 is 3 and for this cycle count the risingedge is plus one skew. Likewise, the indication 0-r0 in column 710indicates that the cycle count for column 710 is 0 and for this cyclecount the rising edge is not adjusted. In similar fashion, theindication 1-rm1 in column 712 indicates that the cycle count for column712 is 1 and for this cycle the rising edge is minus 1 skew. Column 718indicates the skew associated with a particular row in nanoseconds for aspecific combination of frequencies and associated frequency ratio.Column 720 indicates the skew associated with a particular row in termsof the link clock and column 722 provides the general formula for theskew in terms of link and core periods.

The elongated circles indicate the locations of the sample edge detectsand the underline indicates the cycle in which the coincident risingedges occur. By way of example, with respect to row 610 r, the logiclevel sequence [10011001] corresponds to the logic levels generated bysampling link_clock 604 with the rising edge of core_clock 610. Withinthis sequence, the rising sampled edge occurs at the zero-to-onetransition that occurs at cycles 2 and 3 as indicated by the elongatedcircle of logic levels in columns 706 and 708, respectively. Theunderline indicates that the rising edge occurs at cycle 3 (in column708).

FIG. 7B depicts a table 750 further illustrating the different skewsassociated with falling clock edges of the signals depicted in FIG. 6.Similar to rows 610 r-614 r of FIG. 7A, rows 610 f-614 f are tabularrepresentations of the logic levels and skew data associated withcore_clock signals 610-614. Columns 752-766 correspond to the cyclecount and the number of core_clock cycles in a particular timingsequence. Again, column 768 indicates the skew associated with aparticular row in nanoseconds for a specific combination of frequenciesand associated frequency ratio. Column 770 indicates the skew associatedwith a particular row in terms of the link clock and column 772 providesthe general formula for the skew in terms of link and core clockperiods. The elongated circles indicate the locations of the sample edgedetects and the underline indicates the cycle in which the coincidentfalling edges occur. By way of example, the levels in row 622 f,[X0X1X0X1], are indicative of the link_clock 604 being sampled with thefalling edge of core_clock 622. It should be appreciated that theindicator X signifies the occurrence of an invalid cycle. The coincidentedges are detected at cycle 0 as indicated by the encircled one-to-zerotransition.

FIG. 8 depicts a table 800 illustrating the different skews associatedwith the rising and falling clock edges relative to operational modes ofthe validation circuitry. Rows 602, 610-614, and 622-626 represent aportion of the logic levels and skew data associated with core_clocks602, 610-614, and 622-626. Columns 708-714 represent the link clocklevels sampled on the rising core_clock edges as presented in FIG. 7Aand columns 756-762 represent the link clock levels sampled on thefalling core_clock edges as presented in FIG. 7B. Column 802 indicatesfor which skews the Wait-for-Zero (WFZ) mode and Wait-for-Zero 2 (WFZ2)mode are appropriate. Column 804 indicates for which skews the AssumeStart Stable (SS) mode and Assume Start Stable 2 (SS2) mode areappropriate. Column 806 indicates the skew associated with a particularrow as expressed in nanoseconds for a specific combination offrequencies and associated frequency ratio. Column 808 indicates theskew associated with a particular row in terms of the link clock andcolumn 810 provides the general formula for the skew in terms of linkand core clock periods.

In the illustrated tabular format, reference numeral 812 depicts thezero crossing condition that may be detected in either the Wait-for-Zeromode or Wait-for-Zero 2 mode. As may be recalled, the zero crossingcondition occurs when the rising edge jumps forward or backward betweenprevious and current samples but the falling edge stays constant. Withrespect to reference numeral 812, the rising edge is jumping between 0and m1 and the falling edge is staying constant. Reference numeral 814depicts the current falling edge condition that may be detected in theAssume Start Stable mode or Assume Start Stable 2 mode. As will berecalled, the current falling edge condition is exemplified by thedetection of a clean falling edge that has no other falling edges aboutit.

Furthermore, those skilled in the art should appreciate upon referencehereto, in particular, the various MUX arrangements shown in FIGS.5A-5C, that in Assume Start Stable and Assume Start Stable 2 modes, anembodiment of the present invention is operable with the falling edgesampling of the first clock signal alone during phase detection, therebydispensing with the generation and propagation of the cr_edge signal.Additionally, although the link clock signal (i.e., the faster clock) issampled using the core clock signal (i.e., the slower clock) in theillustrated embodiment of phase detection, it should be apparent thatclock sampling may also be performed in opposite, i.e., the slower clocksignal may be sampled using the faster clock signal for purposes of thepresent invention. Clearly, concomitant modifications will be requiredin the logic as well as signal levels and edges (i.e., with respect tofalling/rising edges, logic highs and lows, et cetera), mutatismutandis, in such an embodiment.

FIG. 9 depicts one embodiment of sync generation circuit 204 whichincludes a sync circuit portion 900, a link sync generator circuit,i.e., first sync generator 902, and a core sync generator circuit, i.e.,second sync generator, 904. The sync circuit portion 900 receives theedge_valid signal and generates a start_syncs_h_ff signal, i.e., a startsync signal, substantially centered around the coincident rising edges.More specifically, the edge_valid signal is received by a syncgeneration state machine 906 that generates a set of state signalsindicative of a cycle count. In one embodiment, the state signal is astate_ff[2:0] signal. Each state signal is received by a flip flop 908which asserts a state_ff signal that is fed back to the sync generationstate machine 906 so that the sync generation state machine 906 can runthrough all of its states. The state_ff signal is also provided to astart sync logic circuit 910 that receives the ratio signal in order togenerate a start_syncs signal, i.e., an initial start sync signal. Aflip flop 912 delays the start_syncs signal by one cycle and forwards astart_syncs ff signal to a flip flop 914 which samples thestart_syncs_ff signal with the falling edge of the core_clock signal inorder to shift the start_syncs_ff signal one-half of a cycle and assertthe start_syncs_h_ff signal, which is substantially centered about thecoincident rising edges.

As previously alluded to, the start_syncs_h_ff signal is forwarded tocore sync generation circuitry 904 that includes a flip flop 916, a coresync generator 918, and flip flops 920-926. Initially, the flip flop 916receives the start_syncs_h_ff signal, holds the start_syncs_h_ff signalfor one cycle and asserts a start_core_sync_ff signal that is receivedby the core sync generator 918. The start_core_sync_ff signal initiatesthe core sync generator 918 which, based upon the ratio signal, producesa core_sync_ff signal that is stagged through flip flips 922-926 toproduce a sync_c pulse in the core clock domain. As illustrated, thecore_sync_ff signal returns to the core sync generator. Moreover, thecore sync generator asserts a core_cycle_ff [2:0] signal that is sampledby flip flop 920 and returned to the core sync generator 918. Thefeedback loops provided for the core_cycle_ff signal and thecore_sync_ff signal help maintain the pulse generation performance ofthe core sync generator 918.

Additionally, the start_syncs_h_ff signal is forwarded to link syncgeneration circuitry 902 that is disposed in the link clock domain. Thecircuitry of the link sync generation circuit 902 is analogous to thatof the core sync generation circuit 904. A flip flop 928 receives thestart_syncs_h_ff signal and asserts a start_link_sync_ff signal that isreceived by the link sync generator 930. A ratio signal is clocked withthe link_clock signal by flip flops 932 and 934 before being provided tothe link sync generator 930. The link sync generator 930 produces alink_sync_ff signal which is sampled with the link_clock by flip flop938 and sampled with the link_clock by flip flops 940-944. The resultingsync_l signal comprises the synchronization pulse for the link clockdomain. Flip flop 936, which is associated with a link_cycle_ff signal,and flip flop 938, which is associated with the link_sync_ff signal,provide feedback loops with respect to the link sync generator 930.

One skilled in the art should recognize that the output-stage flip floparrangement shown in FIG. 9, i.e., flip flops 924 and 926 in the path ofsync_c and flip flops 940, 942 and 944 in the path of sync_l, isamenable to many variations and may be provided in one embodiment aspart of the respective domain's delay/distribution tree depending onactual design implementation.

FIG. 10 depicts a timing diagram 1000 associated with the syncgeneration circuit 204 of FIG. 9. Again, a clock frequency ratio of 5:4is exemplified between the link_clock signal and core_clock signal. Acycle count refers to the numbering of core_clock cycles in a particulartiming sequence. In particular, the timing diagram 1000 illustrates thatthe edge_valid signal is received by the sync generation state machine906 which generates a state count for purposes of generating appropriatesync pulses in the link and core clock domains. Based on the ratiosignal, the sync generation state machine counts from 0 to a maximumvalue (which is 7 in the illustrated embodiment due to state_ff[2:0]).The start sync logic circuit 910 (in FIG. 9) generates the start_syncssignal such that start_syncs_ff is asserted when state_ff [2:0] is 4(which is cycle 3, i.e., the cycle before the coincident rising edges).The start_syncs_ff signal is delayed one-half of a cycle by flip flop914. This results in the start_syncs_h_ff signal which is substantiallycentered about the coincident rising edges. With respect to the coresynchronization circuit 904, the start_syncs_h_ff signal is delayed afurther half cycle by flip flop 916. The start_core_sync_ff signalinitiates the generation of the core_cycle_ff signal which initiates thegeneration of the core_sync_ff signal, which in turn initiates thegeneration of the core_cycle_ff signal, and so on. As explained beforewith respect to FIG. 9, the core_sync_ff signal is appropriately stagedso as to be provided as the sync_c signal. Similarly, with respect tothe link synchronization circuit 902, the start_syncs_h_ff signal isdelayed a half cycle by flip flop 928. Thereafter, start_link_sync_ffsignal initiates the generation of the link_cycle_ff signal whichinitiates the generation of the link_sync_ff signal, which in turninitiates the generation of the link_cycle_ff signal, and so on. Again,as before with respect to FIG. 9, the link_sync_ff signal isappropriately staged through flip flops 940-944 so as to be provided asthe sync_l signal.

FIG. 11 depicts one embodiment of a synchronizer pulse generationmethod. At block 1100, the first clock signal is sampled with the secondclock signal to determine coincident rising edges of the first andsecond clock signals. At block 1102, the coincident rising edges arevalidated based upon skew tolerance between the first and second clocksignals. At block 1104, a valid edge signal is generated that isindicative of validated coincident rising edges. The valid edge signalmay be verified by either detecting coincident edges, e.g., Assume StartStable or Assume Start Stable 2 modes, or detecting zero crossings,e.g., Wait-for-Zero or Wait-for-Zero 2 modes, thereby rejectingcoincident edges that may be caused by clock signal aliasing. Hence, theseveral modes of operation provide greater skew tolerance in aconfigurable manner based on the appropriate clock ratios. At block1106, responsive to the valid edge signal, synchronization pulses aregenerated in the first clock domain and synchronization pulses aregenerated in the second clock domain.

FIG. 12 depicts one embodiment of a phase detection method operable withthe circuitry described hereinabove, in particular, with reference toFIGS. 2 and 3. At block 1200, the first clock signal is sampled with arising edge of the second clock signal to assert a first sampled clocksignal having a zero-to-one transition therein that is indicative of thecoincident rising edges in the first and second clock signals. In oneembodiment, the first sampled clock signal is asserted prior to anoccurrence of coincident edges between the first and second clocksignals. It should be appreciated that the logic may be configuredrelative to coincident rising or coincident falling edges. At block1202, the first clock signal is sampled with a falling edge of thesecond clock signal to assert a second sampled clock signal having aone-to-zero transition therein that is indicative of the coincidentrising edges in the clock signals. Similar to the first sampled clocksignal, the second sampled clock signal may also be asserted prior to anoccurrence of the coincident rising edges between the first and secondclock signals. As mentioned with respect to block 1200, the presentmethodology may be effectuated relative to coincident rising orcoincident falling edges. Accordingly, in this embodiment thesynchronizer pulse generator detects coincident edges between two clocksby utilizing logic operating in the slower clock domain, therebyproviding for better timing. In addition, by way of a still furtherembodiment, the methodology of the present invention may effectuatedusing only the second sampled clock signal in certain modes as alludedto hereinabove.

FIG. 13 depicts one embodiment of a sync generation method. At block1300, a start sync signal is generated and substantially centered aroundcoincident rising/falling edges between first and second clock signalsin response to the ratio and a valid edge signal indicative of thecoincident edges. At block 1302, a first synchronization pulse isasserted in the first clock domain in response to the start sync signal.At block 1304, a second synchronization pulse is asserted in the secondclock domain in response to the start sync signal such that the firstand second synchronization pulses are asserted substantiallysimultaneously. Accordingly, the systems and methods described hereinpermit skew-tolerant, high speed sync pulses to be generated fromgeneral PLLs that do not produce sync pulses. Moreover, the systems andmethods described herein allow the skew between the clocks to drift(i.e., drift tolerance) even after the synchronizer pulse generator hasinitially detected coincident edges and started generating sync pulsesaccordingly.

FIG. 14A depicts a portion of a further timing diagram 1400 associatedwith one embodiment of the synchronizer pulse generator wherein a clockfrequency ratio of 4:3 is exemplified between the link_clock signal andcore_clock signal. A cycle count refers to the numbering of core_clockcycles in a particular timing sequence. In particular, the timingdiagram 1400 illustrates the output of flip flops 324-330, AND gate 332,and flip flops 334 and 336 (shown in FIG. 3) as pd_cf1_ff, pd_cf3_ff,pd_cf3_ff, pd_cf4_ff, cf_edge, cf_edge_ff[0], and cf_edge_ff[1],respectively. Initially, the link_clock is sampled on the falling edgesof the core_clock as represented by reference numerals 1402, 1404, and1406, for example. It should be noted that the one-to-zero transitionsare detected during cycle 2 as indicated by reference numerals 1408,1410, and 1412. Additionally, as no skew is present between theillustrated link_clock and core_clock, the system is in a Assume StartStable mode, wherein a falling edge combination corresponding to thelogic combination {-cf_edge & cf_edge_ff[0] & ˜cf_edge_ff[1]} isdetected as indicated by reference numeral 1414.

FIG. 14B depicts a timing diagram 1450 that continues the timing diagram1400 presented in FIG. 14A. In this timing diagram, the output of validedge detect circuit 210, sync generation state machine 906, start synclogic circuit 910, flip flop 912, and flip flop 914 are depicted asedge_valid, state_ff[2:0], start_syncs_ff, and start_syncs_h_ff,respectively. Further, with respect to the core synchronizationcircuitry 904, the output of flip flop 916, flip flop 920, and flip flop922 are depicted as start_core sync_ff, core_cycle_ff, and core sync_ff,respectively. Similarly, with respect to the link synchronizationcircuitry 902, the output of flip flop 928, flip flop 936, and flip flop938 is depicted as start_link sync_ff, link_cycle_ff, and link sync_ff,respectively. Accordingly, it should be appreciated that thesynchronizer pulse generator described herein is applicable to any N:Mclock domain ratios, including clock domain ratios other than 5:4.

Although the invention has been particularly described with reference tocertain illustrations, it is to be understood that the forms of theinvention shown and described are to be treated as exemplary embodimentsonly. Various changes, substitutions and modifications can be realizedwithout departing from the spirit and scope of the invention as definedby the appended claims.

1. A phase detector for a sync pulse generator operable in a clocksynchronizer that effectuates data transfer between first circuitrydisposed in a first clock domain and second circuitry disposed in asecond clock domain, wherein said first clock domain is operable with afirst clock signal and said second clock domain is operable with asecond clock signal, said first and second clock signals having a ratioof N first clock cycles to M second clock cycles, where N/M≧1,comprising: at least one first flip flop operable to sample said firstclock signal with a rising edge of said second clock signal, said atleast one first flip flop thereby operating to assert a first sampledclock signal having a zero-to-one transition therein that is indicativeof coincident rising edges in said first and second clock signals; andat least one second flip flop operable to sample said first clock signalwith a falling edge of said second clock signal, said at least onesecond flip flop operating to assert a second sampled clock signalhaving a one-to-zero transition therein that is indicative of coincidentrising edges in said first and second clock signals.
 2. The phasedetector as recited in claim 1, wherein said at least one first flipflop comprises two flip flops operable to sample said first clock signalwith a rising edge of said second clock signal.
 3. The phase detector asrecited in claim 1, wherein said at least one second flip flop comprisestwo flip flops operable to sample said first clock signal with a fallingedge of said second clock signal.
 4. The phase detector as recited inclaim 1, wherein each of said first and second sampled clock signals isoperable to be staged via a delay register portion.
 5. The phasedetector as recited in claim 1, wherein said first and second sampledclock signals are operable to be forwarded to validation circuitry forvalidating said coincident rising edges based upon skew tolerancebetween said first and second clock signals and to generate a valid edgesignal responsive thereto.
 6. The phase detector as recited in claim 1,wherein said first clock signal is a link clock signal operable in acomputer system.
 7. The phase detector as recited in claim 1, whereinsaid second clock signal is a core clock signal operable in a computersystem.
 8. The phase detector as recited in claim 1, wherein said ratioof N:M cycles comprises a 5:4 ratio of link-to-core clock signalsoperable in a computer system.
 9. The phase detector as recited in claim1, wherein said ratio of N:M cycles comprises a 4:3 ratio oflink-to-core clock signals operable in a computer system.
 10. A phasedetection method for a sync pulse generator operable in a clocksynchronizer that effectuates data transfer between first circuitrydisposed in a first clock domain and second circuitry disposed in asecond clock domain, wherein said first clock domain is operable with afirst clock signal and said second clock domain is operable with asecond clock signal, said first and second clock signals having a ratioof N first clock cycles to M second clock cycles, where N/M≧1,comprising: sampling said first clock signal with a rising edge of saidsecond clock signal to assert a first sampled clock signal having azero-to-one transition therein that is indicative of coincident risingedges in said first and second clock signals; and sampling said firstclock signal with a falling edge of said second clock signal to assert asecond sampled clock signal having a one-to-zero transition therein thatis indicative of coincident rising edges in said first and second clocksignals.
 11. The method as recited in claim 10, wherein the operation ofsampling said first clock signal with a rising edge of said second clocksignal comprises sampling a link clock signal with a rising edge of acore clock signal.
 12. The method as recited in claim 10, wherein theoperation of sampling said first clock signal with a rising edge of saidsecond clock signal comprises sampling a core clock signal with a risingedge of a bus clock signal.
 13. The method as recited in claim 10,further comprising the operation of staging each of said first andsecond sampled clock signals via at least one delay register.
 14. Themethod as recited in claim 10, further comprising the operation offorwarding at least one of said first and second sampled clock signalsindicative of coincident rising edges to validation circuitry, saidvalidation circuitry for validating said coincident rising edges basedupon skew tolerance between said first and second clock signals and togenerate a valid edge signal responsive thereto.
 15. The method asrecited in claim 10, wherein said ratio of N:M cycles comprises a 5:4ratio of link-to-core clock signals operable in a computer system. 16.The method as recited in claim 10, wherein said ratio of N:M cyclescomprises a 4:3 ratio of link-to-core clock signals operable in acomputer system.
 17. A phase detector for a sync pulse generatoroperable in a clock synchronizer that effectuates data transfer betweenfirst circuitry disposed in a first clock domain and second circuitrydisposed in a second clock domain, wherein said first clock domain isoperable with a first clock signal and said second clock domain isoperable with a second clock signal, said first and second clock signalshaving a ratio of N first clock cycles to M second clock cycles, whereN/M≧1, comprising: means for sampling said first clock signal with arising edge of said second clock signal to assert a first sampled clocksignal having a zero-to-one transition therein that is indicative ofcoincident rising edges in said first and second clock signals; andmeans for sampling said first clock signal with a falling edge of saidsecond clock signal to assert a second sampled clock signal having a oneto-zero transition therein that is indicative of coincident rising edgesin said first and second clock signals.
 18. The system as recited inclaim 17, wherein said means for sampling said first clock signal with arising edge of said second clock signal further comprises means forsampling a link clock signal with a rising edge of a core clock signal.19. The system as recited in claim 17, wherein said means for samplingsaid first clock signal with a rising edge of said second clock signalfurther comprises means for sampling a core clock signal with a risingedge of a bus clock signal.
 20. The system as recited in claim 17,further comprising means for delaying each of said first and secondsampled clock signals by a predetermined amount.
 21. The system asrecited in claim 17, wherein at least one of said first and secondsampled clock signals indicative of coincident rising edges is operableto be forwarded to validation circuitry, said validation circuitry forvalidating said coincident rising edges based upon skew tolerancebetween said first and second clock signals and to generate a valid edgesignal responsive thereto.
 22. The system as recited in claim 17,wherein said ratio of N:M cycles comprises a 5:4 ratio of link-to-coreclock signals operable in a computer system.
 23. The system as recitedin claim 17, wherein said ratio of N:M cycles comprises a 4:3 ratio oflink-to-core clock signals operable in a computer system.
 24. A phasedetector for a sync pulse generator operable in a clock synchronizerthat effectuates data transfer between first circuitry and secondcircuitry, wherein said first clock domain is operable with a firstclock signal and said second clock domain is operable with a secondclock signal, comprising: at least one first flip flop operable tosample said first clock signal with a rising edge of said second clocksignal; and at least one second flip flop operable to sample said firstclock signal with a falling edge of said second clock signal, saidsampling by said at least one first and one second flip flops producingtransitions indicative of coincident edges between said first and secondclock signals.
 25. The phase detector as recited in claim 24, whereinsaid coincident edges comprise coincident rising edges.
 26. The phasedetector as recited in claim 24, wherein said coincident edges comprisecoincident falling edges.
 27. The phase detector as recited in claim 24,wherein said first clock signal is a link clock signal operable in acomputer system.
 28. The phase detector as recited in claim 24, whereinsaid second clock signal is a core clock signal operable in a computersystem.
 29. The phase detector as recited in claim 24, wherein saidfirst clock signal and said second clock signal define a 5:4 ratio oflink-to-core clock signals operable in a computer system.
 30. The phasedetector as recited in claim 24, wherein said first clock signal andsaid second clock signal define a 4:3 ratio of link-to-core clocksignals operable in a computer system.